法国专利FR3039741A1 LIGHTING CIRCUIT AND VEHICLE LAMP USING THE SAME

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专利摘要:
A step-down converter (20) supplies a control current (IDRV) to a light source (2) and is feedback-controlled so that the control current (IDRV) approaches a target current ( IREF). An open circuit detection circuit (40) compares the potential difference between the input voltage (VIN) and the output voltage (VOUT) of the voltage-reducing converter (20) with a threshold voltage (VTH). ).
公开号:FR3039741A1
申请号:FR1657309
申请日:2016-07-28
公开日:2017-02-03
发明作者:Tomoyuki Ichikawa
申请人:Koito Manufacturing Co Ltd；
IPC主号:

专利说明:

TECHNICAL AREA
The present invention relates to vehicle lamps used in vehicles, etc., and more particularly to the detection of an open circuit fault occurring therein.
BACKGROUND OF THE TECHNIQUE
Halogen lamps and high intensity discharge (HID) lamps have traditionally been the major sources of light for vehicle lamps, particularly headlamps. However, in recent years, to replace these lamps, vehicle lamps using a semiconductor light source such as one or more LEDs (light emitting diode (s)) or a laser diode have begun to appear. .
Vehicle lamps utilizing a semiconductor light source are required to have a function of detecting an open circuit anomaly due to the open circuit destruction of the semiconductor light source from the disconnection of a light source. beam interconnection or the like, and warning thereof on the vehicle side. Figs. 1A and 1B are circuit diagrams of vehicle lamps 1r and 1s which are equipped with a lighting circuit having an open circuit anomaly detection function. These circuits are circuits studied by the present inventor prior to the design of the present invention and should not be considered as part of the prior art.
A lighting circuit 10 shown in Fig. 1A is equipped with a step down converter 20 and an open circuit detection circuit 30r. The lighting circuit 10r is supplied by a voltage Vbat coming from a battery 4 via a switch 6. The down-converter 20 decreases the voltage VBat and supplies a resultant output voltage Vout to a source of light 2. The step-down converter 20 is feedback-controlled by a converter controller (not shown) so that the control current IDrv flowing through the light source 2 approaches a target value IREf which governs the quantity target light of the light source 2.
The open circuit detection circuit 30r shown in Fig. 1A is equipped with a detection resistor Rs for the current detection and a comparator 32r. The detection resistor Rs is inserted into the control current path IDrv and a voltage drop (current detection signal) which is proportional to the control current IDrv is established across the detection resistor Rs. The comparator 32r compares the current detection signal Vis to a threshold voltage Vth.
When the vehicle lamp lr shown in Fig. 1A is normal, a normal control current Idrv flows through the sense resistor Rs and a voltage drop Vis which is greater than the threshold voltage V ™ occurs. On the other hand, if an open circuit anomaly has occurred, no control current Idrv is flowing, whereby the voltage drop Vis becomes substantially equal to 0 V and thus less than the threshold voltage Vth. Accordingly, the output of the comparator 32r has a first level (e.g., high) indicating that the vehicle lamp lr is normal when Vis> Vjh and a second level (e.g., low) indicating the appearance of an open circuit anomaly when VK <Vjh ·
The open circuit detection circuit 30s shown in FIG. 1B is equipped with resistors R11 and R12 and a comparator 32s. The resistors R11 and R12 divide the output voltage VolJT of the step-down comparator 20. The comparator 32s compares the divided output voltage (voltage sense signal) Ws with a threshold voltage Vth.
When the vehicle lamp ls shown in Fig. 1B is normal, the output voltage νουτ is feedback-controlled at a voltage level that is most suitable for providing a target current.
Iref at the light source 2. If an open circuit fault has occurred, no control current IDrv is flowing and the controller of the buck converter 20 increases the duty cycle, so that the control current IDrv is approaching the target value IDRv, as a result of which the output voltage νουτ increases. As a result, the voltage detection signal Vvs exceeds the threshold voltage Vjh ·
Accordingly, the output of the comparator 32s has a first level (e.g. a high level) indicating that the vehicle lamp ls is normal when VVs <Wh and a second level (e.g., a low level) indicating the appearance of an open circuit anomaly when VVs> Vjh ·
SUMMARY OF THE INVENTION 1. The present inventor has studied the 10 and 10s lighting circuits shown in Figs. 1A and 1B and has discovered the following problems.
For purposes of maintenance or testing, vehicle lamps with a laser diode as a light source 2 may be required to operate in a low luminance mode (test mode) in which causes illumination of the light source 2 at a low luminance level. In this case, in the illumination circuit 10 shown in Fig. 1A, it is necessary that the threshold voltage Vjh be set to a lower value than the voltage detection signal Vis occurring in the low luminance mode. However, in the low luminance mode the control current Idr flowing through the light source 2 is low and thus the voltage detection signal V S is very small. Accordingly, it is necessary that the threshold voltage Vjh be set to a very low value and thus the open circuit detection circuit 30r is likely to be affected by an error.
The light source 2 may consist of a series connection of a plurality of LEDs and bypass switches which are connected in parallel to a plurality of respective ones of the LEDs. With this light source 2, the LED which is connected in parallel to a bypass switch can be controlled on / off according to the activation or deactivation of the bypass switch.
In this case, the output voltage V0UT of the step-down converter 20 is given by
Vout "VF x N where N is the number of LEDs lit. As a result, the output voltage V0ut varies dynamically as a function of the number N of lit LEDs. In the illumination circuit 10s shown in Fig. 1B, it is difficult to properly determine the threshold voltage Vjh when the output voltage V0m dynamically varies. 2. The inventor has also discovered the following problems that relate to an open circuit fault.
Semiconductor light sources are vulnerable to overcurrent. In particular, in the laser diodes, a COD (catastrophic optical damage) can be produced by overcurrent and it is thus necessary to prevent the flow of a current that is greater than an absolute maximum rated current, even instantaneously. Thus, laser diodes require more protection against overcurrent than other light sources.
Instability (switching repetition between contacts (normal state) and no contact (open circuit state)) may occur at the connector contact between the illumination circuit 10r (or 10s) and the light source 2. In the open-circuit state, the current detection signal VK of the lighting circuit 10r becomes 0 V, and thus the duty cycle is increased so that the control current Idrv approaches the target value Iref as a result of which the voltage across the output capacitor increases. If a contact state of the connector contact is subsequently restored, the excess portion of the charge stored in the output capacitor flows in the light source 2, producing an overcurrent.
The present invention has been realized in view of the above circumstances, and an object of the present invention is accordingly to provide a lighting circuit capable of properly detecting an open circuit anomaly. Another object of the present invention is to provide a lighting circuit capable of preventing overcurrent.
[Means for solving problems] 1. A first aspect of the present invention provides a lighting circuit comprising a step-down converter which supplies a control current to a light source through the output inductor and is feedback controlled so that the control current approaches a target current; and an open circuit sensing circuit which compares the potential difference between the input voltage and the output voltage of the step-down converter to a prescribed threshold voltage.
If an open-circuit fault has occurred in the down-converter load, the control current becomes zero and feedback is made in a direction tending to increase the output voltage to increase the control current, so that the input-output potential difference of the step-down converter approaches zero. According to this lighting circuit, an open circuit anomaly can be detected based on the input-output potential difference of the step-down converter.
The open circuit detection circuit may comprise a bipolar pnp transistor whose emitter and base are respectively connected to the input terminal and the output terminal of the down-converter. The activation and deactivation of the bipolar transistor respectively correspond to the absence of detection and the detection of an anomaly. A cost reduction is achieved because no voltage comparator is needed.
The open circuit detection circuit may further include a first resistor which is provided between the collector of the bipolar transistor and the ground.
The open circuit detection circuit may comprise a p-channel FET whose source and gate are respectively connected to the input terminal and the output terminal of the down-converter. Activation and deactivation of the TEC corresponds respectively to the absence of detection and the detection of an anomaly. A cost reduction is achieved because no voltage comparator is needed.
The open circuit detection circuit may further include a blocking element which is provided between the gate and the source of the TEC. Thanks to this measurement, the gate-source voltage can be kept lower than the breakdown voltage.
The open circuit detection circuit may further include a second resistor that is provided between the drain of the TEC and the ground. 2. A second aspect of the present invention provides a lighting circuit comprising a converter having an output inductance, providing a control current to a light source through the output inductor, and is controlled by feedback, so that the control current approaches a target current; and a protection circuit which interrupts the switching operation of the converter during an interruption time upon detection of the return of an open circuit state to the normal state at the output terminal of the converter.
If an open circuit state occurs, the detection value of the control current becomes 0 A and thus, the duty cycle of the converter is increased thereby increasing its output voltage. Upon return to the normal state, the excess portion of the charge stored in the output capacitor is supplied to the light source through the output inductor. Since the output inductance constitutes a resonance circuit with the output capacitor, a limited resonance current flows through the light source and thus overcurrent is prevented.
If the 1s resonance current were superimposed on a control current generated by the feedback control, an overcurrent would occur. On the other hand, by delaying the restart of the switching operation of the converter when returning from an open circuit state to the normal state, a control current appears after the current flow through the resonance circuit is become weak, so that overcurrent can be prevented.
The protection circuit may be such as to estimate that a return from an open circuit state to the normal state has occurred when the output voltage of the converter has dropped rapidly. The phrase "the output voltage of the converter has dropped rapidly" for example covers an event such as the fact that the gradient of the output voltage has exceeded a prescribed threshold value, the fact that the variation of the output voltage during a prescribed time has exceeded a prescribed threshold value, or that the output voltage has been subject to a prescribed variation in a shorter time than a prescribed time. A return from an open circuit state to the normal state can be detected in this way.
The protection circuit is such as to slowly increase the switching ratio of the converter after the interruption time has elapsed. With this measurement, the control current increases slowly until the switching operation is restarted and thus an overcurrent can be prevented more reliably.
The protection circuit is such as to set the target current equal to 0 A during the interruption period and slowly increase the target current after the interruption time has elapsed.
The protection circuit may be such as to interrupt the switching operation of the converter during an interruption time upon detection of a return from a state of a short circuit to the normal state at the output terminal. of the converter. By delaying the restarting of the converter switching operation at the moment of returning from a short-circuit state to the normal state, a control current appears after the current flowing through the resonance circuit has become low, so that overcurrent can be prevented.
The protection circuit may be such as to estimate that a return from a state of a short circuit to the normal state has occurred when the output voltage of the converter has increased rapidly. The return of a state of short circuit to the normal state can be detected in this way.
The protection circuit may comprise a differentiation circuit or a high-pass filter which receives the output voltage of the converter and judges that a return to the normal state has occurred as soon as the output signal of the differentiation circuit or the high pass filter has exceeded a prescribed value.
The protection circuit may comprise a capacitor having one end connected to ground, a load resistor connected to the other end of the capacitor and applying to the capacitor a target voltage which determines the target current in the normal state, and a discharge switch which is provided in parallel with the capacitor and activated upon detection of return to normal state.
The converter may be a step down converter, and the lighting circuit may further include an open circuit detection circuit that compares the potential difference between the input voltage and the output voltage to a prescribed threshold voltage. of the converter.
A third aspect of the present invention provides a vehicle lamp comprising a light source and any of the lighting circuits described above controlling the light source.
This aspect of the present invention makes it possible to properly detect an open circuit anomaly. The first aspect of the present invention makes it possible to properly detect an open circuit anomaly. The second aspect of the present invention prevents overcurrent.
BRIEF DESCRIPTION OF THE DRAWINGS The invention will be better understood and its advantages will be better understood on reading the detailed description which follows. The description refers to the following drawings, which are given by way of example.
FIGS. 1A and 1B are circuit diagrams of vehicle lamps which are equipped with a lighting circuit having an open circuit anomaly detection function.
Fig. 2 is a circuit diagram of a vehicle lamp according to a first embodiment of the present invention.
Fig. 3 is a waveform block diagram of an illumination circuit shown in Fig. 2.
Figs. 4A and 4B are circuit diagrams respectively showing the specific vehicle lamp configurations.
Figs. 5A and 5B are circuit diagrams showing the configuration of another specific vehicle lamp.
Fig. 6 is a circuit diagram of a vehicle lamp according to a second embodiment.
Fig. 7 is an operating waveform diagram of an illumination circuit shown in Fig. 6.
Fig. 8 is a circuit diagram showing a specific version of the lighting circuit shown in Fig. 6.
Fig. 9 is an operating waveform diagram of the lighting circuit of Fig. 8.
Fig. 10 is a circuit diagram showing the configuration of a specific version of a protection circuit.
Fig. 11 is a circuit diagram showing an operation that is performed upon a return from a short-circuit state to the normal state.
Fig. 12 is a circuit diagram of a protection circuit according to a modification.
Fig. 13 is a perspective view of a lamp unit which is equipped with the vehicle lamp according to the first or second embodiment.
DETAILED DESCRIPTION
Preferred embodiments of the present invention will be described hereinafter with reference to the drawings. Identical or equivalent components are given the same reference symbols in the drawings and their redundant description may be omitted as appropriate. The embodiments are only examples and should not be construed as limiting the present invention, and the features to be described in the embodiments or combinations thereof are not necessarily essential to the present invention.
In this description, a state such as "a component A is connected to a component B" covers not only the case where the components A and B are connected directly to each other but also the case where they are connected indirectly to each other. to one another via another component having substantially no influence on their state of electrical connection or affecting the function or effect to be achieved by their connection.
Similarly, a state such as "a component C is provided between components A and B" covers not only the case where components A and C or components B and C are connected directly to one another, but also the case where they are indirectly connected to each other via another component having substantially no influence on their state of electrical connection or affecting the function or effect to be obtained by their connection.
In this description, a symbol representing an electrical signal such as a voltage signal or a current signal or a circuit element such as a resistor or a capacitor represents its voltage, current, resistance, capacitance or the like. if necessary.
Those skilled in the art will understand that a replacement between a bipolar transistor, a MOSFET and an IGBT (insulated gate bipolar transistor), a replacement between a p-channel transistor (or pnp) and an n-channel transistor (or npn) ), the permutation between the hot spot and the mass of a power source is possible. (Embodiment 1)
Figure 2 is a circuit diagram of a vehicle lamp 1 according to a first embodiment. The vehicle lamp 1 is equipped with a light source 2 and a lighting circuit 10. The lighting circuit 10 is equipped with a down-converter 20, a controller 22 and a open circuit detection circuit 40.
The lighting circuit 10 is powered by a voltage VBat from a battery 4 via a switch 6. The down-converter 20 decreases the input voltage Vin which corresponds to the battery voltage VBat and provides a resultant output voltage V0ur to a light source 2. The step-down converter 20 is feedback-controlled by a converter controller 22, so that the control current Idrv flowing through the light source 2 approaches a target value Iref which governs the amount of target light of the light source 2.
The down-converter 20 comprises an input capacitor C1, an output capacitor C2, a switching transistor M1, a rectifying diode DI and an inductance L1. The controller 22 generates a pulse signal Spwm whose duty cycle is varied so that the control current Idrv approaches the target value IREf and controls the switching transistor Ml using the pulse signal Spwm. particular limitation to the control method of the controller 22; it can be either a hysteresis command (all or nothing command) or a feedback command using an error amplifier.
The open-circuit detection circuit 40 compares with a prescribed threshold voltage Vjh the potential difference ΔV between the input voltage VIN and the output voltage V0ut of the step-down converter 20. If AV> Vjh, the detection circuit open circuit 40 estimates that the lighting circuit 10 is normal and outputs an anomaly detection signal SI having a first level (for example, the high level). If AV <Vjh, the open circuit detection circuit 40 judges that an open circuit fault has occurred and outputs an abnormality detection signal SI having a second level (e.g., the low level).
The basic configuration of the lighting circuit 10 has been described above. A description of how it works will then be done. FIG. 3 is an operating waveform diagram of the lighting circuit 10 shown in FIG. 2. Before the time t0, the vehicle lamp 1 is normal and the control current Idrv is stabilized at the target value Iref - In this state, the output voltage V0ut is stabilized at a certain voltage level.
If an open circuit fault occurs at time t0, the control current IDrv is cut off and becomes 0 A. The controller 22 increases the duty cycle of the pulse signal Srwm to make the control current IDrv closer to the target value In response, the output voltage V0ut increases and soon becomes equal to the input voltage ViN. The open circuit detection circuit 40 which monitors the potential difference AV (= VIN-V0ut) causes the fault detection signal SI to go low when the relationship AV <Vjh is set at time t1.
The way in which the lighting circuit 10 operates has been described above. The lighting circuit 10 can detect an open circuit anomaly based on the input-output potential difference AV of the step-down converter 20.
An open circuit anomaly can be properly detected, even in the case where the lighting circuit 10 is used in a vehicle lamp 1 having a laser diode as the light source 2 and the lighting circuit 10 is put in a low luminance mode in which the control current IDrv is set to a low value. An open circuit anomaly can also be properly detected, even in the case where the lighting circuit 10 is used in a vehicle lamp 1 in which the light source 2 comprises a series connection of LEDs and an activation command / Deactivation is performed for it by bypass switches, regardless of the dynamic variation of the output voltage V0ut ·
The present invention is to be understood based on the circuit diagram of FIG. 2 which includes the blocks and encompasses various devices and circuits which are determined from the above description. Thus, the present invention should not be construed as being limited to any particular configuration. More specific configurations will be described below to facilitate understanding of the essentials and operation of the circuit of the present invention and to clarify them rather than to narrow the scope of the present invention.
Figs. 4A and 4B are circuit diagrams respectively showing specific vehicle lamp configurations 1a and 1b. An open circuit detection circuit 40a shown in FIG. 4A comprises a pnp bipolar transistor 42, a first resistor R1 and a base resistor R3. The emitter of the bipolar transistor 42 is connected to the input terminal of the step-down converter 20 and its base is connected to the output terminal of the step-down converter 20 through the base resistor R3. The first resistor RI is provided between the collector of the bipolar transistor 42 and the ground. The first resistor RI may be omitted to provide an open collector output. The basic resistance R3 can also be omitted.
The AV input-output potential difference of the step-down converter 20 is applied as input between the base and the emitter of the bipolar transistor 42. When the vehicle lamp is normal, since the potential difference ΔV is sufficiently large, the bipolar transistor 42 is activated and the anomaly detection signal SI is high (Vin). If an open circuit anomaly has occurred, the input-output potential difference ΔV becomes lower than the base-emitter threshold voltage (0.6 to 0.7 V) of the bipolar transistor 42 as a result of which the bipolar transistor 42 is deactivated and the anomaly detection signal SI is at the low level. That is to say that the activation and deactivation of the bipolar transistor 42 respectively correspond to the absence of detection and the detection of an anomaly. Thus, the vehicle lamp shown in Figure 4A allows a reduction in the cost of the circuit because it does not require a voltage comparator.
An open circuit detection circuit 40b shown in FIG. 4B is considered a circuit obtained by replacing the bipolar transistor 42 of the open circuit detection circuit 40a shown in FIG. 4A by a p-channel TEC 44. The source of the TEC 44 is connected to the input terminal of the buck converter 20 and its gate is connected to the output terminal of the buck converter 20 through a gate resistor R4. A second resistor R2 is provided between the drain of the TEC 44 and the ground. A blocking element 46 is provided between the gate and the source of the TEC 44 and blocks the gate-source voltage so that it does not exceed a prescribed value. The blocking element 46 may be a zener diode, a Schottky diode or the like.
The AV input-output potential difference of the step-down converter 20 is inputted between the gate and the source of the TEC 44. When the vehicle lamp lb is normal, since the potential difference Δv is sufficiently large, the TEC 44 is activated and the anomaly detection signal SI is at the high level (Vin). If an open circuit fault has occurred, the AV input-output potential difference becomes lower than the threshold voltage Vgscth) (for example, 1.5 V) of the TEC 44, as a result of which the TEC 44 is deactivated. and the anomaly detection signal SI is at the low level. That is, the activation and deactivation of the TEC 44 correspond respectively to the absence of detection and to the detection of an anomaly. Thus, the vehicle lamp lb shown in FIG. 4B makes it possible to reduce the cost of the circuit because it does not require a voltage comparator.
Figs. 5A and 5B are circuit diagrams showing the configuration of another vehicle lamp. As shown in FIG. 5A, an open circuit detection circuit 40c of the vehicle lamp uses a voltage comparator 48. The voltage comparator 48 can compare the output voltage V0m to a voltage obtained by shifting a Vjh voltage offset the VON input voltage on the low voltage side. The voltage offset Vjh is produced by a level shifter 49.
Fig. 5B is a circuit diagram showing the configuration of an exemplary level-shifter 49. The level-shifter 49 includes, for example, a resistor R5 and a current source 50. One end of the resistor R5 is connected to the input terminal of the buck converter 20 and the other end is connected to the current source 50. The current source 50 generates a prescribed constant current Ic. A voltage VIN-R5 x ïc appears at the point of connection of the resistor R5 and the current source 50. That is, the voltage R5 x serves as an offset voltage Vth ·
Through the use of the voltage comparator 48, the vehicle lamp allows for accurate voltage comparison at the cost of increased cost. If a comparator circuit having a plurality of voltage comparators is used and an additional voltage comparator remains, no cost increase will occur. [Embodiment 2]
Fig. 6 is a circuit diagram of a vehicle lamp ld according to a second embodiment. A connector 12 is provided for example between a light source 2 and a lighting circuit 10d, so that the light source 2 and the lighting circuit 10d are removably connected to each other. The lighting circuit 10d is equipped with a step-down converter 20d, a controller 22 and a protection circuit 60. The technique which will be described in the second embodiment can be used in combination with that which has been described in the first embodiment. Accordingly, the lighting circuit 10d may be equipped in addition to the open circuit detection circuit described above 40, although omitted from FIG. 6.
The lighting circuit 10d is different from the lighting circuit 10 shown in FIG. 2 in that it is further provided with an output inductance L2 between the capacitor C2 and the light source 2. detecting that the output terminals of the buck converter 20d have returned from an open circuit state to the normal state, the protection circuit 60 interrupts the switching operation of the buck converter 20d for a time interruption xl.
The protection circuit 60 can for example detect the return of an open circuit state to the normal state based on the output voltage V0Ut of the down-converter 20d. After the interruption time x1 has elapsed, the protection circuit 60 can slowly increase the switching duty cycle of the step-down converter 20d from zero (soft start).
The basic configuration of the lighting circuit 10d has been described above. A description of how it works will then be done. FIG. 7 is an operating waveform diagram of the illumination circuit 10d shown in FIG. 6. Before the time t1, the connector 12 is in the open circuit state in which the control current IDRV is equal at 0 A. The controller 22 controls the switching transistor M1 with a large duty cycle by means of feedback control to increase the control current IDrv from 0A and bring it closer to the target value IREf · Accordingly a current flows in the output capacitor C2 through the inductor L1 and the output voltage V0ut becomes higher than it is in the normal state.
At time t1, the capacitor 12 is again properly activated and restores a state of contact (normal state). As a result, the excess portion of the charge stored in the output capacitor C2 is supplied to the light source 2 through the output inductor L2. Since the output inductance L2 constitutes an LC resonant circuit 14 with the output capacitor C2, a limited resonance current circulates in the light source 2 and overcurrent is thereby prevented. Attention should be paid to the fact that in the absence of output inductance L2, the lamp current Ilamp flowing through the light source 2 would increase without being limited as indicated by the dashed line in FIG. overcurrent.
The lamp current Ilamp is the sum of the control current Idrv which is generated by the step-down converter 20d by a feedback control and the resonance current 1s which flows through the resonance circuit 14. Since the resonance current 1s circulates through the loop formed by the output capacitor C2 and the output inductance L2, the current detection signal VK which is supplied to the controller 22 does not include the resonance current 1res- Accordingly, if the protection circuit 60 restarted a switch operation of the down-converter 20d just after the return of the open circuit state to the normal state (i.e., the interrupt time x1 was omitted), a Resonance current 1s is superimposed on the control current Idrv generated by the feedback control and the lamp current Ilamp can flow through the light source 2 in the form of an overcurrent.
On the other hand, in this embodiment, at the moment of the return of an open circuit state to the normal state, the protection circuit 60 restarts a switching operation of the down-converter 20d after the interruption time has elapsed. tl. The interruption time t1 can be determined taking into account the relaxation time necessary for the resonance current 1res to become sufficiently small. Thanks to this measurement, the control current IDrv appears after the resonance current 1res of the resonance circuit 14 has decreased, so that an overcurrent can be prevented.
If a soft start command has not been performed when a switching operation restarts after the interruption time t1 has elapsed, an overcurrent may occur due to the resonance of the inductance L1 of the output capacitor C2 and the output inductance L2. On the other hand, in this embodiment, such an overcurrent can be prevented by slowly increasing the output current IDrv of the step-down converter 20d by a soft start.
The configuration of a specific version of the lighting circuit 10d shown in FIG. 6 will then be described. FIG. 8 is a circuit diagram of a specific version of the lighting circuit 10d shown in FIG. 6. The controller 22 which performs a hysteresis control (on-off control), is equipped with an amplifier of current detection 70, a hysteresis comparator 72 and a driver 74. A detection resistor Rs is inserted for example in the control current path IDrv which is generated by the voltage-reducing converter 20d. The current sensing amplifier 70 amplifies the voltage drop V S across the sense resistor Rs. The hysteresis comparator 72 compares the boosted voltage drop Vis to a, selected depending on its output, two voltages. threshold VH and Vl and thus generates modulated control pulses. The threshold voltages VH and VL are determined as a function of a reference voltage VREf which governs the target value IREf of the control current IDrv. The driver 74 controls the switching transistor M1 based on the control pulses generated by the hysteresis comparator 72. Alternatively, the control method of the controller 22 may be a feedback control using an error amplifier.
As shown in FIG. 7, the output voltage V0m drops instantly when returning from an open circuit state to the normal state (at time t1). The protection circuit 60 can detect a return to the normal state using this phenomenon. That is, the protection circuit 60 can estimate that a return from an open circuit state to the normal state has occurred when the output voltage V0m has dropped rapidly.
The protection circuit 60 may include, for example, a first differentiation circuit 62 or a low-pass filter. The absolute value of the output signal VA of the first differentiation circuit 62 increases, for example, as the downward slope of the output voltage Vour becomes steeper. The output signal VA then returns to 0 V with the gradient which varies as a function of the time constant TCI of the first differentiation circuit 62. The interruption time τΐ mentioned above is determined by the time constant TCI.
A target current controller 64 sets the reference voltage Vref which governs the target value IREf of the control current IDrv according to the output signal VA of the first differentiation circuit 62. More specifically, the target current controller 64 sets the reference voltage VREf to a normal value VNorm if the absolute value of the output signal VA of the first differentiating circuit 62 is less than a prescribed threshold value VB. In the state where the absolute value of the output signal VA of the first differentiation circuit 62 is greater than the threshold value VB, the target current controller 64 sets the reference voltage VREF to 0 V (and thus the target current IREF at 0 A), so that the switching operation of the step-down converter 20d is interrupted.
If the absolute value of the output signal VA of the first differentiation circuit 62 becomes lower than the threshold value VB / the target current controller 64 slowly increases the reference voltage VREF (target current IREF) to the normal value VN0RM. This makes it possible to carry out a progressive start after the interruption time t1 has elapsed.
Fig. 9 is an operating waveform diagram of the illumination circuit 10d of Fig. 8 and shows how the illumination circuit 10d operates when a suitable contact state of the connector contact 12 is restored. When a suitable contact state of the connector 12 is restored to the time t1, the output voltage V0m drops rapidly and the absolute value of the output signal VA of the first differentiation circuit 62 then increases beyond the threshold value VB. As a result, the reference voltage VREF drops to 0 V from the normal value VNOrm and the switching operation of the down converter 20d is interrupted.
The absolute value of the voltage VA then decreases as a function of the time constant TCI of the first differentiation circuit 62 and becomes smaller than the threshold value VB at time t2. In response, the target current controller 64 slowly increases the reference voltage VREF. With the above operation, the delay time of time t1 at time t2 serves as the interruption time t1.
Fig. 10 is a circuit diagram showing the configuration of a specific version of the protection circuit 60. The first differentiation circuit 62 mainly comprises a bipolar transistor Q11, a capacitor C21 and a resistor R21. With this configuration, the first differentiation circuit 62 generates a signal Va which represents the gradient of the downward slope of the output signal V0m-. The time constant TCI of the first differentiation circuit 62 is determined by the resistor R21 and the capacitor C21. The first differentiation circuit 62 may be considered as a high pass filter.
The target current controller 64 mainly comprises a capacitor C22, a load resistor R22 and a discharge switch Q12. One end of the capacitor C22 is connected to ground. The load resistor R22 is used to apply to the capacitor C22 a voltage Vcnt which determines the normal value Vnorm of the reference voltage VREf · When the discharge switch Q12 is deactivated, the voltage Vc22 across the capacitor C22 is equal to the voltage Vcnt -The voltage Mcn across the capacitor C22 is applied to a voltage division circuit, which consists of resistors R23 and R24 through a buffer 66, so that the reference voltage VREf is generated.
The output signal VA of the first differentiation circuit 62 is inputted to the base of the discharge switch Q12, which is a bipolar transistor npn. If the base voltage VA of the transistor Q11 of the first differentiation circuit 62 becomes smaller than the on / off threshold value of its transistor (threshold voltage mentioned above) VB and the output signal VA 'of the first differentiation circuit 62 thus exceeds the base-emitter voltage value VBE of the discharge switch Q12, the discharge switch Q12 is activated, so that the voltage Vc22 across the capacitor C22 and thus the reference voltage Vref become 0 V The discharge switch Q12 is not only a voltage comparison means but also has a reset function of the reference voltage VREf at 0 V.
If the base voltage VA of the transistor Q11 exceeds the threshold value VB, the transistor Q11 is deactivated and the discharge switch Q12 is also deactivated, so that the capacitor C22 is charged via the resistor R22. Meanwhile, the voltage Vm across the capacitor C22 increases with the time constant of CR, TCI. This achieves the soft start mentioned above. Since the transistor Q11 is a pnp bipolar transistor and receives an input voltage V N on its transmitter, it operates with the input voltage V IN as a reference. It must therefore be borne in mind that the transistor Q11 is activated when the voltage VA becomes lower than the threshold value VB and deactivated when the voltage VA becomes greater than the threshold value VB.
When the buffer 66 has a long response time delay, a transistor Q13 is added. When the signal VA 'exceeds the threshold voltage VBE (= VB) of the transistor Q13, the transistor Q13 is activated and draws directly downwards at 0 V a reference voltage VREF appearing at the connection node of the dividing circuit. voltage which consists of the resistors R23 and R24. when the buffer 66 operates at high speed, the transistor Q13 and the resistors R23 and R24 may be omitted. (Modifications of embodiment 2) (Modification 2.1)
Although the technique for preventing overcurrent when returning from an open circuit state to the normal state has been described above, this technique can also be used to prevent overcurrent at the time of return of a state of short circuit in the normal state. This can be done in such a way that the protection circuit 60 interrupts the switching operation of the step-down converter 20d during an interrupt time x2 when detecting the return of a short-circuit state to the state. normal at the output terminal of the protection circuit 60. The interruption time% 2 may be the same as the interruption time xi or different.
Fig. 11 is a waveform diagram showing an operation that is performed when returning from a short circuit state to the normal state. In a short-circuit state, the output voltage Vout is set to a voltage close to 0 V. The control current IDrv which is generated by the step-down converter 20d is stabilized at a target value IRef, even in the short circuit state. When returning from the short-circuit state to the normal state (time t1), the output voltage Vout goes high. Accordingly, when the output voltage V0ur of the step-down converter 20d has increased rapidly, the protection circuit 60 can estimate that a return from a state of a short circuit to the normal state has occurred.
The protection circuit 60 may include a second differentiation circuit 62s (for example, that shown in Fig. 12) or a low pass filter instead of the first differentiation circuit 62 described above. The output signal of the second differentiation circuit 62s increases as the upward slope of the output voltage Vout becomes steeper. The output signal of the second differentiation circuit 62s then returns to 0 V with the gradient which varies as a function of the time constant TC2 of the second differentiation circuit 62s. This modification can thus prevent an overcurrent at the time of the return from a state of short circuit. (Modification 2.2)
A protection circuit may be configured to take into account both the return from an open circuit state and the return from a short circuit state. For example, two protection circuit systems 60 may be provided for a return from an open circuit state and a return from a short circuit state. Alternatively, a configuration shown in Fig. 8 is possible, wherein two differentiation circuit systems, i.e., a first differentiator circuit 62 for a return from an open circuit and a second differentiator circuit 62s for a return from a short circuit state, and a common target current controller 64 are provided.
Fig. 12 is a circuit diagram of a protection circuit 60e according to modification 2.2. The protection circuit 60e is different from the protection circuit 60 of FIG. 10 in that it is further provided with a capacitor C23. The capacitor C23 constitutes a second differentiation circuit 62s for a return of a short-circuit state with a base resistor R12 of the transistor Q12 and a base resistor R13 of the transistor Q13. The second differentiation circuit 62s generates voltages Va and Va as a function of the gradient of the positive edge of the output voltage Vour. Transistors Q12 and Q13 are activated when the respective voltage signals Va and Va of the second differentiation circuit 62s exceed a value prescribed VB.
The output signals Va and Va of the second differentiation circuit 62s increase as the upward slope of the output voltage V0Ut becomes steeper. The output signals Va and Va then return to 0 V with the gradients which vary according to the time constant TC2 of the second differentiation circuit 62s. The interruption time x2 of the return from a short-circuit state is determined by the time constant TC2.
The protection circuit 60e of FIG. 12 can prevent an overcurrent both at the time of the return of an open circuit state to the normal state and the return of a short circuit state to the normal state. A protection circuit obtained by suppressing the first differentiating circuit 62 of the protection circuit 60e of FIG. 12 can prevent an overcurrent when returning from a short circuit state to the normal state. (Use)
A description will finally be made of how the vehicle lamps 1 and 1d are used. Fig. 13 is a perspective view of a lamp unit (lamp assembly) 500 which is equipped with the vehicle lamp 1 or ld according to the first or second embodiment. The lamp unit 500 is equipped with a transparent cover 502, a high beam unit 504, a low beam unit 506 and a body 508. The vehicle lamp 1 or ld described hereinabove The vehicle lamp 1 or ld can be used for each low beam unit 506 instead of or in addition to the high beam unit 504. .
Although the present invention has been described above in the form of embodiments using the specific terms, the embodiments merely indicate the principle and applications of the present invention and various modifications and variations of the arrangement of the components are possible for the embodiments without departing from the concept of the present invention as described in the claims.

权利要求:
Claims (17)
[1" id="c-fr-0001]
A lighting circuit (10) characterized by comprising: a converter (20) having an output inductor (L2), providing a control current (IDrv) to a light source (2) by means of intermediate of the output inductance (L2) and is feedback controlled so that the control current (idrv) approaches a target current (IrEF); and a protection circuit (60) which interrupts the switching operation of the converter (20) during an interruption time upon detection of the return of an open state to a normal state at the terminal of output of the converter (20).
[2" id="c-fr-0002]
2. Lighting circuit (10) according to claim 1, characterized in that the protection circuit (60) estimates that the return of an open circuit state to the normal state has occurred when the output voltage (V0ut) of the converter (20) dropped quickly.
[3" id="c-fr-0003]
Illumination circuit (10) according to Claim 1 or 2, characterized in that the protection circuit (60) interrupts the switching operation of the converter (20) during an interruption time during the detection of a return of a state of short circuit in the normal state at the output terminal of the converter (20).
[4" id="c-fr-0004]
4. Lighting circuit (10) characterized in that it comprises: a converter (20) which comprises an output inductor (L2), supplies a control current (IDrv) to a light source (2) by means of intermediate of the output inductance (L2) and is feedback controlled so that the control current (IDrv) approaches a target current (IREf); and a protection circuit (60) which interrupts the switching operation of the converter (20) during an interruption time upon detection of the return of a normal state short-circuit state to the terminal output of the converter (20).
[5" id="c-fr-0005]
5. Lighting circuit (10) according to claim 3 or 4, characterized in that the protection circuit (60) estimates that the return of a state of short circuit to the normal state has occurred when the output voltage (νουτ) of the converter (20) increased rapidly.
[6" id="c-fr-0006]
6. Lighting circuit (10) according to any one of claims 1 to 5, characterized in that the protection circuit (60) increases or decreases slowly the duty cycle switching of the converter (20) after the lapse of time. 'interruption.
[7" id="c-fr-0007]
Illumination circuit (10) according to one of Claims 1 to 6, characterized in that the protection circuit (60) comprises a differentiation circuit (62) or a high-pass filter which receives the output voltage (VOMO of the converter (20) and considers that the return to the normal state has occurred as soon as the output signal of the differentiation circuit (62) or the high-pass filter has exceeded a prescribed value.
[8" id="c-fr-0008]
8. lighting circuit (10) according to any one of claims 1 to 7, characterized in that the protection circuit (60) comprises: a capacitor whose end is connected to ground; a load resistor (R22) which is connected to the other end of the capacitor and applies to the capacitor a target voltage which determines the target current (Iref) in the normal state; and a discharge switch (Q12) which is provided in parallel with the capacitor and activated upon detection of the return to normal state.
[9" id="c-fr-0009]
9. Lighting circuit (10) characterized in that it comprises: a converter (20) which comprises an output inductor (L2), supplies a control current (IDrv) to a light source (2) by means of a intermediate of the output inductance (L2) and is feedback controlled so that the control current (Idrv) approaches a target current (IREf); and a protection circuit (60) which interrupts the switching operation of the converter (20) during an interruption time when the output voltage (V0ljt) of the converter (20) has varied rapidly.
[10" id="c-fr-0010]
10. Lighting circuit (10) according to any one of claims 1 to 9, characterized in that the converter (20) is a converter (20) voltage step down; and in that the illumination circuit (10) further comprises an open circuit detection circuit which compares the potential difference between the input voltage and the output voltage (V0Ut) of the converter (20) to a voltage prescribed threshold (Vjh).
[11" id="c-fr-0011]
Illumination circuit (10) according to claim 10, characterized in that the open circuit detection circuit comprises a bipolar pnp transistor (42) whose emitter and base are respectively connected to the input terminal and at the output terminal of the converter (20).
[12" id="c-fr-0012]
12. Lighting circuit (10) characterized in that it comprises: a voltage-reducing converter (20) which supplies a control current (IDrv) to a light source (2) via the inductor output (L2) and is feedback controlled so that the control current (IDrv) approaches a target current (ïREf); and an open circuit detection circuit which compares with a prescribed threshold voltage (Vjh) the potential difference between the input voltage and the output voltage (Vout) of the voltage down converter (20).
[13" id="c-fr-0013]
Illumination circuit (10) according to claim 12, characterized in that the open circuit detection circuit comprises a bipolar pnp transistor (42) whose emitter and base are respectively connected to the input terminal and at the output terminal of the voltage-reducing converter (20).
[14" id="c-fr-0014]
The illumination circuit (10) according to claim 13, characterized in that the open circuit detection circuit further comprises a first resistor (RI) which is provided between the collector of the bipolar transistor and the ground.
[15" id="c-fr-0015]
15. Lighting circuit (10) according to claim 12, characterized in that the open circuit detection circuit comprises a p-channel FET whose source and gate are respectively connected to the input terminal and the terminal. outputting the voltage-reducing converter (20).
[16" id="c-fr-0016]
The illumination circuit (10) according to claim 15, characterized in that the open circuit detection circuit further comprises: a blocking element (46) provided between the gate and the source of the p-channel FET; and a second resistor (R2) provided between the drain of the p-channel FET and the ground.
[17" id="c-fr-0017]
Vehicle lamp characterized by comprising: a light source (2); and the lighting circuit (10) according to any one of claims 1 to 16 which controls the light source (2).

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同族专利:

公开号 | 公开日

DE102016214014A1|2017-02-02|

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FR3039741B1|2020-11-27|

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法律状态:
2017-05-29| PLFP| Fee payment|Year of fee payment: 2 |

2018-04-06| PLSC| Publication of the preliminary search report|Effective date: 20180406 |

2018-06-08| PLFP| Fee payment|Year of fee payment: 3 |

2020-05-26| PLFP| Fee payment|Year of fee payment: 5 |

2021-05-26| PLFP| Fee payment|Year of fee payment: 6 |

优先权:

申请号 | 申请日 | 专利标题

JP2015152676|2015-07-31|

JP2016040218A|JP6687425B2|2015-07-31|2016-03-02|Lighting circuit and vehicle lamp using the same|

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